Self-organizing control system



Aug. 5, 1969 R. L. BARRON 3,460,096

SELF-ORGANIZING CONTROL SYSTEM FIG, 1, 5L @ce o/Gv/w- Typ/v4 .nar- @26m/wma; can/reu SYSTEM Fae JVA/64E Ve/ILE F76. 2. mace .ofeww- Paw' favo/r/a/v//YG 0G/c INVENTOR. eme/e z.. aeeO/V,

Aug. 5, 1969 R. L. BARRON 3,460,096

SELF-ORGANIZING CONTROL SYSTEM Pneu .my 14. 196e 11 sheets-sheet s upI Aaa 'c-7- c2 nv y frJe/VEYS.

Aus. 5, 1969 R. L. BARRON 3,460,096

SELF-ORGANIZING CONTROL SYSTEM FIG. SJW/verzon@ a/mwn- Faeroe/mmf ,affix/Mimi, TYPE 1' IN VEN TOR. @065e L. ameeofv,

R. L. BARRON SELF-ORGANIZING CONTROL SYSTEM Aug. 5? 1969 11 Sheets-Sheet 5 Filed July 14, 1966 IN1/ENT R.

f 5 ,f A ,Mana/Kd ,4r-faena; Y6

Aug. 5, 1969 R. L. BARRON SELF-ORGANIZING CONTROL SYSTEM 11 Sheets-Sheet 7 Filed July 14. 1966 xlvx /Xll R. WEI w Q (CS U m .sto

Ausg-5,1969 R. L. BARRON 3,460,096

S ELF-ORGANI Z ING CONTROL SYSTEM Filed July 14. 1966 11 Sheets-Sheet S F76. 12. Fanano/vm smfMr/c-By e065@ L 34690,

AU@ 5, 1969 R. L.. BARRQN SELF-ORGANIZING CONTROL SYSTEM 11 Sheets$heet 9 Filed July 14. 1966 INVENTOR. P0655 1.. menen/v,

. 411mm I f Wa/1L,

.WH .QQ

A? T TOIC'NE Y6.

Aug. 5, 1969 Filed July 14, 1966 R. l.. BARRoN 3,460,096

SELF-ORGANIZING CONTROL SYSTEM 11 Sheets-Sheet 10 11 Sheets-Sheet 11 R. L. BARRON SELF-ORGANIZTNG CONTROL SYSTEM www Aug. 5, 41969 Filed .my 14. 196e United States Patent O 3,460,096 SELF-ORGANIZING CONTROL SYSTEM Roger L. Barron, 8605 Ardfour Lane,

Burke, Va. 22015 Continuation-impart of application Ser. No. 535,551, Mar. 18, 1966. This application July 14, 1966, Ser. No. 565,162

Int. Cl. G0511 13/02 U.S. Cl. S40-172.5 41 Claims ABSTRACT F THE DISCLOSURE The disclosure relates to a self-organizing control system requiring minimum information storage capable of control of a plant by combining statistical decision theory to determine the true instantaneous plant performance, prediction theory to determine the performance trend, and rapid trial generation to ascertain what must be done to improve the performance trend. This is provided by online sampling and changing of system operation. The disclosure also includes performance assessment units and a probability state variable unit as subcombinations for carrying out the control operation.

The application is a continuation-in-part of applicants previously filed patent application Serial No. 535,551, led March 18, 1966, and entitled Self-Organizing Control System and now abandoned.

This invention relates to self-organizing control systems and, more particularly, to a high-speed self-organizing control system requiring a minimum of information storage. The disclosure in this application describes a selforganizing control system that uses only a short-term record of its control signal experiments and requires essentially no memory for the sequences of system performance values which result during controller operation. Successful high-speed self-organization is accomplished by the system via generation of internal signals representing, at any point in time: (1) polarity of a recent control signal change and (2) instantaneous control system performance.

A main object of the invention is to provide a novel and improved self-organized control system wherein predicted system performance is evaluated on-line either continuously or periodically to modify the course of action pursued by the self-organizing elements of the system.

A further object of the invention is to provide a novel and improved self-organizing control system which employs a performance assessment stage which is highly effective in a Wide range of control system applications, the performance assessment stage being of a nature to be incorporated in a self-contained module which is compatible with a variety of designs of other stages of the over-all system, the module being applicable to many areas directed to problems of a specific type, such as stabilization, control, and dynamic process identification.

A further object of the invention is to provide an improved self-organizing control system employing a novel and efficient probability state variable conditioning logic module, namely, a device which changes its output state in response to a conditioning signal from a performance assessment rnodule, said conditioning logic module basing each change of state on both the level of the received conditioning signal and the internal memory record of that output state change which (acting through the environment) resulted in the conditioning signal, whereby the ability of the conditioning logic module to associate cause and effect, basing its decisions on accumulated statistical evidence concerning the presence of predicted results of its past actions, permits realization of effective self-orga- ICC nizing control actions, the conditioning logic module being applicable to a wide range of situations, from those involving linear, single variable control problems to situations involving multiple, coupled variables and time-varying, nonlinear dynamic environments, and being applicable to many problems of a specific type, such as stabilization, control, and dynamic process identification, as above-mentioned.

A further object of the invention is to provide a novel and improved self-organizing control system employing a dynamic performance assessment means which can process information pertaining to all significant variables of the controlled process, thereby providing computation of a single, unied performance measure which is a function of all significant variables of the controlled process, said unified performance measure being used with multiple conditioning logic modules to generate control action signals for multiple actuation devices, the conditioning logic modules being at least equal in number to the number of such actuation devices, and probability state variable conditioning logic being used in said conditioning logic modules to obtain an eliicient search within the multivariable parameter space represented by said multiple control action signals, thus producing effective control actions capable of involving all actuation devices simultaneously when required.

A further object of the invention is to provide an improved self-organizing control system which produces satisfactory control without the usual reliance on a priori data during design and operation of the system, said a priori data pertaining to the characteristics of the controlled plant and the environment in which it operates, this freedom from reliance on a priori data being accomplished without generating limit cycle oscillations of the controlled variable, elimination of said limit-cycle oscillations being a result of the random output sequences produced by the probability state variable conditioning logic.

A still further object of the invention is to provide an improved self-organizing control system in which the outputs of multiple, parallel, probability state variable conditioning logic modules are summed algebraically to provide with high reliability the control signal for each channel of actuation, said high reliability being a consequence of the tolerance of the self-organzing controller in this parallel configuration for malfunctions or failures of some but not all of the parallel-connected conditioning logic modules, said configuration also providing improved quality of performance of the self-organizing controller by virtue of the additional dynamic range available in the regulating control signal, which additional dynamic range is afforded by the parallel connection of conditioning logic modules.

A yet further object of the invention is to provide an improved self-organizing control system in which the quality of control is not critically sensitive to the amplitudes or frequencies of noise components present in the signals from the sensors, this relative insensitivity to noise being the result of statistical decision processes employed by the probability state variable conditioning logic.

Detailed background discussions of the theory and application of self-organizing control systems would be beyond the scope of this patent application disclosure. A survey of the underlying theory and practice as relates to the self-organizing control system disclosed in this application is Contained in the technical paper Self-Organizing and Learning Control Systems by Roger L. Barron, published in conjunction with the 1966 Bionics Symposium sponsored by the Air Force Avionics Laboratory, Research and Technology Division, Air Force Systems Command, United States Air Force, Wright-Patterson Air Force Base, Ohio, which symposium was conducted May 2-5, 1966, in Dayton, Ohio. Said paper presents, in addition to theoretical matters, the results of an investigation of the application of the self-organizing control systern disclosed in this application to pitch-rate and normalacceleration control of a high-performance aircraft. Reference is also made in the said paper to single-axis and multiple-axis control of orbiting spacecraft; throttle control for aircraft landing approaches; and control of large, exible space launch vehicles.

Further objects and advantages of the invention will become apparent from the following description and claims, and from the accompanying drawings, wherein:

FIGURE 1 is a block diagram of a generalized typical self-organizing control system employing a novel and improved performance assessment stage in conjunction with a novel and improved conditioning logic stage constructed in accordance with the present invention.

FIGURE 2 is a block diagram of the novel and improved conditioning logic stage, or probability state variable (PSV) conditioning logic, employed in the self-organizing control system of FIGURE l.

FIGURE 3 is a block diagram of a first type of novel and improved performance assessment stage which may be employed in the self-organizing control system of FIG- URE 1.

FIGURE 4 is a block diagram of a second type of novel and improved performance assessment stage which may be employed in the self-organizing control system of FIGURE 1.

FIGURE 5 is a functional diagram detailing the operations which comprise the PSV conditioning logic of FIG- URE 2.

FIGURE 6 is a functional diagram detailing the operations which comprise the first type of performance assessment illustrated in FIGURE 3.

FIGURE 7 is a functional diagram detailing the operations which comprise the second type of performance assessment illustrated in FIGURE 4.

FIGURE 8 is a functional schematic detailing the generalized electrical circuit of the P register, P-register control logic, and digital-to-analog conversion of the P- register contents as employed in the PSV conditioning logic of FIGURES 2 and 5.

FIGURE 9 is a functional schematic detailing the generalized electrical circuit of the statistical source as employed in the PSV conditioning logic of FIGURES 2 and 5.

FIGURE l is a functional schematic detailing the generalized electrical circuit of the U register, U-register control logic, and digital-to-analog conversion of the U- register contents as employed in the PSV conditioning logic of FIGURES 2 and 5.

FIGURE l1 is a functional schematic detailing the generalized electrical circuit of the sign Au(t) memory as employed in the PSV conditioning logic of FIGURES 2 and 5.

FIGURE l2 is a functional schematic detailing the generalized electrical circuit of the logic time base as employed in the PSV conditioning logic of FIGURES 2 and 5.

FIGURE 13 is a functional schematic detailing the generalized electrical circuit of the rst type of performance assessment illustrated in FIGURES 3 and 6.

FIGURE 14 is a functional schematic detailing the generalized electrical circuit of the second type of performance assessment illustrated in FIGURES 4 and 7.

FIGURE l is a block diagram depicting a generalized self-organizing control system consisting of a controlled plant involving multiple variables and of a plurality of the PSV conditioning logic stages of FIGURE 2 in conjunction with the performance assessment stage of FIG- URE 3.

Referring to the drawings, FIGURE l diagrammatically illustrates a typical self-organizing control system which employs novel and improved PSV conditioning logic and performance assessment stages constructed in accordance with the present invention. The system illustrated is a closed-loop system consisting of the controlled plant l2 driven by the control signal on channel 21 [11( t)] which is generated by the self-organizing control subsystem 11 based on the system error signal on channel 19 [e(t)] which is formed by a conventional differential amplifier 14 operating on the command input signal on channel 17 and a feedback signal on channel 18 which is produced by a sensor 13 monitoring the plant controlled variable on channel 22. The self-organizing control subsystem 11 consists of the performance assessment stage 15 (to be fully described later) which develops a rewardpunish signal (V) on channel 20 based on the system error signal on channel 19, and the PSV conditioning logic stage 16 (to be fully described later) which generates a plant control signal on channel 21 [u(t)] in response to the reward-punish signal on channel 2l] and an internally-stored history of past directions of change in the u(t) control signal on channel 21. The characteristics of the u(t) control signal on channel 21 furnished to the plant 12 by the self-organizing control subsystem 11 are such as to achieve and maintain a minimum (ideal- Iy zero) system error signal on channel 19 regardless of arbitrary variations in the command signal input on channel 17 and variations in the controlled variable on channel 22 caused by changes within, or external disturbances acting upon the controlled plant l2.

Although the sensor 13 is illustrated as an external function in FIGURE l, it may obviously be incorporated as part of the controlled plant 12, in accordance with wellknown practice, since its only requirement is to deliver to differential amplifier 14 a compatible feedback signal on channel 18 representing the state (controlled variable on channel 22) of controlled plant 12. Alternatively, the sensor 13 could be of the type which generates the error signal on channel 19 directly with the command input signal on channel 17 supplied to the sensor by suitable electrical or other means, in accordance with well-known practice. In any event, the conventional differential amplifier 14 could be incorporated as part of the controlled plant 12, in accordance with standard practice, thereby reducing the required plant interface to the command input signal on channel 17, the system error signal on channel 19 to be delivered to the self-organizing control subsystem 11, and the resultant u(t) control signal on channel 21 generated by control subsystem 11.

The simplest form of self-organizing control system is illustrated in FIGURE l, i.e., a plant requiring control of only a single variable. The novel and improved selforganizing control techniques described in this disclosure are as readily adaptable to a complex, multivariable plant requiring simultaneous control of many related (coupled) or unrelated variables. Dependent upon plant characteristics, a typical self-organizing subsystem as illustrated could be used to control each variable; or a form of selforganizing control subsystem consisting of a single performance assessment stage and several PSV conditioning logic stages could be used to control multiple variables; or a form of self-organizing control subsystem consisting of a single performance assessment stage and multiple PSV conditioning logic stages whose outputs are paralleled by means of a conventional summing amplifier could be used to provide very reliable control of one variable. An extremely useful characteristic of these novel and irnproved self-organizing control techniques when applied to a multi-variable plant is the fact that specic details regarding intervariable coupling (i.e., the interaction or interdependency of variables) need not be known to the designer or user of the self-organizing control system.

It will be readily apparent that in a system such as illustrated in FIGURE l, a vital function to be performed is that of dynamic performance assessment. System performance must be evaluated periodically or continuously to reinforce properly the courses of action taken by the PSV conditioning logic in generating the plant control signal. Since the performance assessment function relates directly to the selected criterion against which system performance is measured, this function tends to be problemspecific, and the performance criterion type and prediction time constant must be selected with attention to the requirements of the specific plant to be controlled. This limitation obviates design of a universal performance assessment function but does not preclude development of broad types of performance assessment function, with each type allowing for some parameter (for example, time constant) adjustability to accommodate widely different plant characteristics. The two types of performance assessment stages illustrated in FIGURES 3 and 4, and described in detail later in this disclosure, are examples of such broad types of performance assessment function.

FIGURE 3 diagrammatically depicts one type of performance assessment function developed as a part of the invention herein disclosed. The essential purpose of performance assessment stage A is to perform a continuous assessment of self-organizing control system performance as a function of the eft) system error signal on channel 19 and to generate a V reward-punish signal on channel based upon this assessment. The criterion used in the type I performance assessment stage 15A for generating the V signal on channel 20 is based on a tangentiallyextrapolated predictive function of system error. The predicted system error signal on channel 55 (ep) is calculated by a predictor function 49, and may be expressed as eD=e(t)-|T(l), where e(t) is the instantaneous system error signal on channel 19 and T is the prediction interval (constant). Since the over-all goal of the system is to reduce e(t) to zero as rapidly as possible without overshoot (which could result in an oscillatory convergence of the error to zero), it is desirable to generate a V signal on channel 20 which produces maximum acceleration until the predicted error changes sign and then an exponential convergence to zero error. A V signal of the form sgn Vzminus sgn ep'sgn "l, produces this result. Qualitatively, this form of V signal rewards those PSV conditioning logic actions which accelerate ep toward zero and punishes those actions which accelerate e,j away from zero, while establishing the desired terminal response along the line e-l-TzO. In theory, a ternary V signal. where -l-l=rewar -l- H-punisl-A, and 0=zero reinforcement, could be employed. In practice. satisfactory results are obtained with a binary V signal, as described in this disclosure, where +1=reward and O=punish.

FIGURE 3 details the basic functions performed by the type I performance assessment stage to generate the above form of V signal. A predictor function 49, incorporating a prediction interval control 54 for flexibility of application, operates on the efr) system error signal on channel 19 to obtain the predicted system error signal en on channel 55, which in turn is operated on by differentiators 51 to obtain its second derivative, n, the signal on channel 57. Sign detectors 50 and 52 monitor ep and n, respectively, to provide sgn ep, the signal on channel 56, and Sgn r'l'p, the signal on channel 58, which, when gated by the reward-punish logic 53, generate the binary V signal on channel 20.

The theory behind the use of the second derivative of the predicted error signal (n) rather than some other derivative is fully set forth in the above noted technical paper entitled Self-Organizing and Learning Control Systems which was incorporated herein by reference. The section thereof entitled Performance Assessment clearly shows mathematically that the sign of the NIch derivative of ep is compared with the sign of ep Where N is the order of the system. It is apparent, as in the above noted technical paper and herein that the system order is two for the preferred embodiment and therefore the second derivative of ep is fed to the reward-punish logic for coniparison with ep.

The operations which comprise the type I performance assessment stage of FIGURE 3 are illustrated in more detail in FIGURE 6. The operation performed by the predictor 49 on the e(r) signal on channel 19 may be expressed approximately as the Laplace transform (l-l-Ts), which yields ep (the signal on channel S5)=e(t)-|-T(t), where T is that period of time selected by prediction interval control S4. The predicted error 6 is then fed to differentiators 51, consisting of differentiator stages and 101 in series, to obtain its second derivative, tip, the signal on channel 57. The ep signal on channel 55 is also processed by a zero-crossing detector 104 and an output buffer (level changer to obtain logiccompatible signals), which comprise sign detector 50, to obtain sgn ep, the signal on channel 56. In like manner, p, the signal on channel 57, is processed by zero-crossing detector 102 and output buffer 103, comprising sign detector 52, to obtain sgn p, the signal on channel 58. The two binary signals, Sgn ep and sgn tip, are then operated on by reward-punish logic 53, which implements the function sgn Vzminus sgn ep-sgn p, to provide the desired binary V signal on channel 20. The type I performance assessment stage 15A output may be expressed as the Boolean functions V=reward=sgn ep-sgn fp U sgn ep-sgn p when the output is a logical one, and

7=Punish:sgn ep'sgn p U sgn ep-sgn r'lp when the output is a logical zero.

The generalized electrical circuit and the circuit interconnections of the type I performance assessment stage 15A of FIGURES 3 and 6 are detailed by the functional schematic of FIGURE 13. Specific component values and supply voltages are not shown since they are unique to the characteristics of a given controlled plant and to the characteristics of the components (such as the operational amplifiers, logic gates, and transistors) used for hardware implementation of the functional schematic.

The predictor 49 operates on the e(l) signal on channel 19 approximately per the Laplace transform (I+Ts) to obtain the ep signal on channel S5 [epzeftH-TUH. The prediction interval T is selected by prediction interval control 54. Conventional operational amplifier 174, capacitors C1A (or, in its place, C1B, CIC, or CID) and C2, and resistors R1, R2, and R3 comprise a standard augmented differentiator with a double high frequency cutoff, whose output is the sum of the input and its first derivative, and whose input is relatively insensitive to high frequency noise. The ratio of resistors R3 and R2 establishes the amplification factor (unity in this case) applied by amplifier 174 to the e(t) signal on channel 19. The time constant formed by resistor R3 and capacitor C1A (or. in its place, C1B, CIC, or CID) determined the prediction interval T. Resistor R1 connected to capacitor C1A (or, in its place, C1B, CIC, or CID) limits the high frequency response of predictor 49, and capacitor C2 shunting resistor R3 doubles the amount of attenuation of input frequencies higher than this limit, with both effects combining to render predictor 49 insensitive to high frequency noise which could mask the derivative output.

The predicted error signal ep on channel 55 is then fed to dilferentiator 100, a standard differentiator with double high frequency cutoff, which consists of conventional operational amplifier 175, capacitors C3 and C4, and resistors R4 and R5. to obtain thc cp signal on channel 106. The period of differentiation is established by resistor R5 and capacitor C3, while resistor R4 and capacitor C4 provide the required attenuation of high frequency noise. An identical dilferentiator 101 in series, consisting of operational amplifier 176. capacitors C5 and C6, and resistors R6 and R7, provides the second derivative of predicted error, the p signal on channel 57. Sign detector 50, consisting of zero-crossingr detector 104 and output buffer 105, then operates on the ep signal on channel S5 to obtain the required binary sgn ep, the signal on channel 56. Sign information is extracted from the ep signal on channel 55 by emitter-coupled clippers 181 and 182, and is then Operated on by level changer 183 and shaper 184. In an identical manner, the p signal on channel 57 is processed by sign detector 52, consisting of zero-crossing detector 102 and output buffer 103, to provide the sgn ip signal on channel 58. Sign information is extracted by emitter-coupled clippers 177 and 178, and then transformed to the proper binary signal by level changer 179 and shaper 180.

The signs of the predicted error and its first derivative are then processed by reward-punish" logic 53 to form the binary V signal on channel 20. First, inverters 185 and 186 generate sgn eD and sgn 'p, respectively. AND- gate 187 then forms the logical product sgn epsgn p, and

AND-gate 188 forms the logical product sgn epsgn r'fp. The balance of the exclusive-OR function is performed by OR-gate 189 which forms the logical sum of logical products, sgn el, -sign p U sgn ep-sgn p, defined as V, the type I performance assessment stage A output parameter, the signal on channel 20.

FIGURE 4 diagrammatically illustrates a second type of performance assessment function developed as a part of the present invention. As in performance assessment stage 15A, the purpose of performance assessment stage 15B is to perform a continuous assessment of self-organizing control system performance as defined by the e(1) system error signal on channel 19 and to generate a V (rewardpunish") signal on channel 20 based upon this assessment. The criterion used in the type II performance assessment stage 15B also uses a tangentially-extrapolated predictive function of system error. Starting with the expression used for V in the type I performance assessment stage 15A (l/:minus sgn ep'sgn p), and making the restrictive assumption that sgn p=sgn up, we obtain the expression V=minus sgn ep-sgn up, where ep=e(t)|-Te(t) and we define up as a predicted value of the plant control signal, up=ku(t)-l-T1(t). As in the type I performance assessment stage 15A, this form of V signal 20 rewards those PSV conditioning logic actions which accelerate ep toward zero, and punishes those actions which accelerate ep away from zero. In the type III performance assessment stage 15B, V, the signal on channel 20, is implemented as a binary signal where a logical one indicates a reward" decision and a logical zero indicates a punish decision. Predicted system error, the signal on channel 65, is calculated by a pred1ctor function 59, and may be expressed as ep=e(t)l-T(t), where e(t) is the instantaneous system error signal on channel 19 and T is the prediction interval const ant selected by the prediction interval control 64. Alsimtlar predictor function 61, with a fixed prediction interval based on specific controlled plant 12 characteristics, operates on the 1:(t) plant control signal on channel 21 to obtain a predicted value of the plant control signal, the signal on channel 67. Sign detectors 60 and 62 monitor ep and up, respectively, to provide sgn ep, the signal on channel 66, and sgn up, the signal on channel 68, which, when gated by the reward-punish logic 63, generate the binary V signal on channel 20.

The operations which comprise the type Il performance assessment stage of FIGURE 4 are illustrated in greater detail in FIGURE 7. The operation performed by the predictor 59 on the e(t) signal on channel 19 may be expressed approximately as the Laplace transform (l-l-Ts), which yields ep (the signal on channel 65): e(t)-l-Te'(t), where T is that period of time selected by prediction interval control 64. In like manner, the u(t) plant control signal on channel 21 is operated on by predictor 61 approximately per the Laplace transform (kA-TIS) to obtain up (the signal on channel 67): ku(t)l-T1(t), where k is a fixed gain, and T1 is a fixed prediction interval and k and T1 are chosen such that Llp,

sgn up=sgn unless u is at one of its limits, in which event sgn up=sgn u. The el, signal on channel 65 is processed by a zero-crossing detector 107 and an Output buffer 108 (level changer to obtain logic-compatible signals), which comprise sign detector 60, to obtain sgn ep, the signal on channel 66. In an identical manner, up, the signal on channel 67, is processed by zero-crossing detector 109 and output buffer 110, comprising sign detector 62, to obtain sgn up, the signal on channel 68. The two binary signals, sgn el, and sgn up, are then operated on by reward-punish logic 63, which implements the function sgn v=minus sgn ep-sgn up, to provide the desired binary V signal on channel 20. The type II performance assessment stage 15B output may be expressed as the Boolean function V:reward=sgn ep'sgn up U sgn ep-sgn up when the output is a logical one, and

when the output is a logical zero.

The generalized electrical circuit and the circuit interconnections of the type II performance assessment stage 15B of FIGURES 4 and 7 are detailed by the functional schematic of FIGURE 14. Specific component values and supply voltages are not shown since they are unique to the characteristics of a given controlled plant and to the characteristics of the components (such as the operational amplifiers, logic gates, and transistors) used for hardware implementation of the functional schematic,

The predictor 59 operates on the e(1) signal on channel 19 approximately per the Laplace transform (l-l-Ts) to obtain the ep signal on channel 65 [ep=e(t)l-Te(t)]. The prediction interval T is selected by prediction interval control 64, Conventional operational amplifier 190, capacitors C7A (or, in its place, C7B, C7C, or C7D) and C8, and resistors R8, R9 and R10 comprise a standard augmented diferentiator with a double high frequency cutoff, whose output is the sum of the input and its first derivative, and whose input is relatively insensitive to high frequency noise. The ratio of resistors R10 and R9 establishes the amplification factor (unity in this case) applied by amplifier to the e(t) signal on channel 19. The time constant formed by resistor R10 and capacitor C7A (or, in its place, C7B, C7C, or C7D) determines the prediction interval T. Resistor R8 connected to capacitor C7A (or, in its place, C7B, C7C, or C7D) limits the high frequency response of predictor 59, and capacitor C8 shunting resistor R10 doubles the amount of attenuation of input frequencies higher than this limit, with both effects combining to render predictor 59 insensitive to high frequency noise which could mask the derivative output.

The operations performed by predictor 61 on the 14(1) signal on channel 21 are similar to the operations performed by predictor 59. The approximate Laplace transform (k-l-Tls) is implemented by predictor 61 to obtain the up signal on channel 67 [up=ku(t)i-T11i(t)]. Conventional operational amplifier 195, capacitors C9 and C10, and resistors R11, R12, and R13 comprise a standard augmented differentiator with a double high frequency cutoff, whose output is the sum of the input and its first derivative, and whose input is relatively insensitive to high frequency noise. The ratio of resistors R13 and R12 establishes the amplification factor k applied by amplifier to the u(t) signal on channel 21. The time constant formed by resistor R13 and capacitor C9 specifies the prediction interval T1. Resistor R11 connected to capacitor C9 limits the high frequency response of predictor 61, and capacitor C10 shunting resistor R13 doubles the amount of attenuation of input frequencies higher than this limit, with both effects combining to render predictor 61 insensitive to high frequency noise which could mask the derivative output.

The predicted error signal ep (the signal on channel 65) is then operated on by sign detector 60, consisting of zero-crossing detector 107 and output buffer 108, to obtain the required binary sgn ep, the signal on channel 66. Sign information is extracted from ep, the signal on channel 65, by emitter-coupled clippers 191 and 192, and is then operated on by level changer 193 and shaper 194. In an identical manner, up, the signal on channel 67, is processed by sign detector 62, consisting of zero-crossing detector 109 and output buffer 110, to provide sgn up, the signal on channel 68. Sign information is extracted by emitter-coupled clippers 196 and 197, and then transformed to the proper binary signal by level changer 198 and shaper 199.

The signs of the predicted system error and the predicted value of the plant control signal are then processed by reward-punish logic 63 to form the binary V signal on channel 20. First, inverters 200 and 201 generate sgn ep and sgn up, respectively. AND-gate 202 then forms the logical product sgn ep-sgn up, and AND-gate 203 forms the logical product sgn ep-sgn up. The balance of the exclusive-OR function is performed by OR-gate 204 which forms the logical sum of logical products defined as V, the type II performance assessment stage 15B output parameter, the signal on channel 20.

It is apparent from the foregoing descriptions that the type I performance assessment stage 15A of FIGURES 3 and 6 and the type II performance assessment stage 15B of FIGURES 4 and 7 perform the same basic functions of continuous assessment of self-organizing control system performance based on the system error signal, e(t), and both generate a reward-punish signal, V, based upon this assessment. Further, both types of performance assessment stage use a predictive function of system error. This predictive function need not consist of the simple tangential extrapolation described above but may employ nonlinear or higher-order linear prediction. However, tangential extrapolation, which is theoretically optimum for linear, second-order controlled plants, is adequate for linear plants of higher than second order and many nonlinear plants.

The dissimilarities between the type I and type II performance assessment stages lie in the criteria employed to generate their respective V signals, and in the resultant dependence upon, or independence of, certain characteristics of the specific controlled plant. In review, the criterion upon which type I performance assessment stage 15A bases its V signal is sgn v=minus sgn ep-sgn p, in which the sign of the predicted error is coordinated with the sign of the acceleration of predicted error. If the latter has the opposite sign from the former, a reward signal level is generated by stage 15A and sent to the PSV conditioning logic stage 16. Conversely, if the signs of the predicted error and the acceleration of predicted error are the same, a punish signal level is generated by stage 15A to guide the PSV conditioning logic. The PSV conditioning logic stage 16 then determines which direction of the plant control signal on channel 21 produced the particular reward or punish assessment. It is therefore immaterial, for this configuration of self-organizing control system, whether the controlled plant polarity (p/up) is positive or negative: the type I performance assessment stage 15A working in conjunction with the PSV conditioning logic stage 16 will experimentally determine this information.

As explained earlier, the type II performance assessment stage 15B bases its V signal upon the criterion sgn v=minus sgn ep-sgn up. This criterion was developed by making the restrictive assumption that sgn p=sgn up, where up=ku(t)l-T1u(z). The sign of the predicted system error is now coordinated in a fixed way with the sign of an extrapolated value of the plant control signal, u(t),

with an immediate advantage of less sensitive circuitry required for hardware implementation, due to elimination of differentiators and 101 (FIGURE 13). As in the type I performance assessment, a reward signal level is generated by stage 15B if the signs of ep and up are dissimilar and a punish signal level is generated if the signs of ep and up are identical. The lack of sign information for predicted error acceleration requires that the controlled plant polarity (Bp/up) be known a priori, as this configuration of the self-organizing control system cannot determine plant polarity through experimentation. (For the purpose of this development, plant polarity was assumed to be negative; a positive polarity would require that the V signal on channel 20 be cornplemented.) This disadvantage is more than ollset for many applications by the absence of the p term in the performance assessment criterion, making operation of the self-organizing control system much less sensitive to environmental and sensor noise and to the order of the controlled plant.

As illustrated in FIGURE l, the V (rewardpunish") signal on channel 20 generated by performance assessment stage 15 is supplied to the PSV conditioning logic stage 16. In turn, PSV conditioning logic stage 16 utilizes the V signal on channel 20 and an internally-stored history of directions of change of the 11(1) plant control signal on channel 21 to increment the u(t) signal on channel 21. The direction of the increment of the uU) signal on channel 21 supplied to the controlled plant 12 by the self-organizing control subsystem 11 is that direction which will minimize the e(t) system error signal on channel 19, resulting from a comparison of the command input signal on channel 17 and the sensed signal on channel 18 which represents the controlled plant output variable on channel 22. In brief, the PSV conditioning logic stage 16 functions as a signal generator whose output signal magnitude and sign are based on a continuous dynamic assessment of actual plant performance versus desired plant performance. The successful accomplishment of this function by the PSV conditioning logic stage 16 is due to its ability to associate cause and effect, basing its decisions on accumulated evidence concerning the present or predicted results of its past actions, thereby permitting realization of effective control even though characteristics of the controlled plant are incompletely known to the control system designer and user.

FIGURE 2 diagrammatically defines the functions comprising the PSV conditioning logic stage developed as a part of the present invention. The PSV conditioning logic stage 16 consists of: a U register 28 which, with its associated control logic 27 and digital-to-analog (D/A) converter 29, increments, stores, converts, and buffer amplifies the u(h) plant control signal appearing on channel 21; a statistical source 26, whose probabilistically-biased random noise output signal on channel 38 controls the incrementation of the U register 28; a P register 24, which, with its associated control logic 23 and digital-to-analog (D/A) converter 25, generates the probability control voltage, vp, the signal on channel 37, that controls the probability of the statistical source output signal on channel 38 being at the logical one or logical zero level; a sign Au(t) memory 30, which stores the directions of change in the u(t) plant control signal on channel 21 and provides the sgn Au signal on channel 48 that, in conjunction with the V signal on channel 20 from a performance assessment stage 15, determines the direction of incrementation of the P register 24; and a logic time base 31, whose function is to generate the clock pulses (C1, the signal on channel 43; C2, the signal on channel 44; C3, the signal on channel 45; C4, the signal on channel 46; and C5, the signal on channel 47) which control the sequence of events associated with each increment of the u(t) control signal on channel 21. In summation, the operation of the PSV conditioning logic stage 16 is such that the probabilities associated with alternative directions of change of the output variable, uU), which is the plant control signal on channel 21, are biased in favor of changes which produced desirable results, as indicated by the state of the V signal on channel as generated by the performance assessment stage 15. The sequence of major events occurring during each sample period is: (1) the P register 24 is incremented, thus changing the output statistics of the statistical source 26, (2) the U register 28 is incremented in accordance with the new probabilities, and (3) the direction of the U register 28 increment is stored in the sign Au(t) memory 30. l

The operations which comprise the PSV conditioning logic stage of FIGURE 2 are illustrated in greater detail in FIGURE 5. The P-register control logic 23, consisting of add-subtract decision logic 69 and decision memory 70, generates the ADD signal on channel 34 and the SUBTRACT signal on channel 35, which determine the direction of the increment of P register 24. Add-subtract decision logic 69 correlates the V signal on channel 20 from the performance assessment stage 15 with the sgn Au signal on channel 48 representing the change in the utf) signal on channel 21 which resulted in the reward-punish decision. The form of this correlation is such that a positive increment to the P-register 24 contents is ordered if the V signal on channel 20 indicates a reward and the sgn Au signal on channel 48 indicates the associated change in the u(t) signal on channel 2l was a positive increment, or if the V signal on channel 20 indicates a punis and the sgn Au signal on channel 48 indicates the associated change in the u(t) signal on channel 21 was a negative increment. Conversely, a negative increment to the P-register 24 contents is ordered if the V signal on channel 20 indicates a reward and the sgn Au signal on channel 48 indicates the associated change in the u(t) signal on channel 21 was a negative increment, or if the V signal on channel 20 indicates a punish" and the sgn Au signal on channel 48 indicates the associated change in the utf) signal on channel 21 was a positive increment. At the occurrence of clock pulse C1, the signal on channel 43 generated by the logic time base 31, the decision of add-subtract logic 69 is stored in decision memory 70, which provides the ADD signal on channel 34 and the subtract signal on channel 35 to the P register 24. These P-register control signals are described by the Boolean functions ADDIV sgnnu U T sgnAu and SUBIl/-sgnAu l.) V-sgndu The P register 24 consists of counter up-down steering logic 71 and a 3-stage reversible counter 72. The function implemented by P register 24 is that of a standard 3-bit binary up-down counter, with seven of the eight possible counter states untilized. Limit gates within countter up-down steering logic 71 monitor the contents of the 3-stage reversible counter 72 and detect the counts of one and seven. The counter up-down steering logic 71 senses the level of the ADD signal on channel 34 and the SUBTRACT signal on channel 35 at the occurrence of the clock pulse C2, the signal on channel 44 generated by the logic time base 31, and generates a COUNT- UP signal on channel 90 if the ADD signal on channel 34 is true and a count of seven is not detected in the 3-stage reversible counter 72. Conversely, a COUNT- DOWN signal on channel 91 is generated if the SUB- TRACT signal on channel 35 is true and a count of one is not detected in the 3-stage reversible counter 72. If the 3-stage reversible counter 72 is in either the one state or the seven state, it remains in that state until a true ADD signal on channel 34 or a true" SUBTRACT signal on channel 35, respectively, is sensed at the time of occurrence of the C2 signal on channel 44. The COUNT-UP signal on channel 90 is thus described by the Boolean function The contents of P register 24, the signal on channel 36, are processed by D/A converter 25 to generate vp, the signal on channel 37, which in turn controls the probability of the statistical source (SS) 26 output, which is the signal on channel 38, being in the logical one state or the logical zero state. A count of four in P register 24 results in a 50 percent probability that the SS output signal on channel 38 will be in the logical one state at any given instant of time, while a count of seven results in approximately a percent probability that the SS output signal on channel 38 will be in the logical one state and a count of one results in approximately a 5 percent probability that the SS output signal on channel 38 will be in the logical one state. Intermediate counts in P register 24 result in intermediate probabilities for a logical one state or a logical zero state to occur at the SS output at any given instant of time. Although an approximately linear relationship between the contents of P register 24 and the probability of the SS output signal on channel 38 being in the logical one state was implemented in the invention herein described, a linear relationship is not required. The operation of PSV conditioning logic 16 and the self-organizing control system could be improved by appropriate nonlinearities in the relationship, although the benefits from this are slight. The chief restriction is that any positive increment in P-register 24 contents must result in an increase in probability of a logical one state and any negative increment in P-register contents must result in a decrease in probability of a logical one state.

The D/A converter 25 consists of precision bit-weight resistors 73 and operational amplifier 74. The actual D/ A conversion is performed by precision bit-weight resistors 73, which comprise a standard resistive summation network. One end of a precision resistor is connected to the true output of each counter stage of the P register 24, and the other ends of the resistors are tied in common, forming a summation point. Since the value of each of the precision resistors diters from the value of adjacent resistors by a power of two, with the lowest value connected to the most significant bit and the highest value connected to the least signicant bit of P register 24, the summation point provides an analog voltage level, the signal on channel 92, accurately represents the contents of P register 24. This analog voltage level is then amplitied by operational amplifier 74 to provide the bipolar probability control voltage, vp, the signal on channel 37, applied to the statistical source 26.

Basically, the statistical source 26 is a signal generator whose output, nrtp), the signal on channel 38, is a probabilistically-biased random sequence of logical ones and logical zeroes. The statistical source consists of a random noise generator 76, a threshold comparator 75, and an output buffer 77. The random noise generator 76 generates a random noise output, 11 the signal on channel 93, with an approximately Gaussion distribution. The threshold comparator 75 then compares the random noise, signal, nr, on channel 93, with the probability control voltage, vp, the signal on channel 37, to generate a random binary sequence having a duty cycle (ratio of the number of logical ones to logical zeroes occurring over a statistically-meaningful period of time) which is in direct proportion to the magnitude and polarity of vp, the signal on channel 37. A probability control voltage of zero (P-register 24 contents equal four) results in a duty cycle of approximately 50 percent, while a maximum negative voltage (P-register 24 contents equal seven) results in a duty cycle of approximately 95 percent and a maximum positive voltage (P-register 24 contents equal one) results in a duty cycle of approximately 5 percent.

An output buffer 77 then transforms this prohabilisticallybiased signal to levels compatible with the logic gates of the U-register control logic 27, thereby providing the statistical source output, n,(p), the signal on channel 38, which consists of a random sequence of logical ones and logical zeroes with a probabilistically-controlled duty cycle.

The U-register control logic 27, consisting of add-subtract decision logic and memory 78, generates an ADD signal on channel 39 and a SUBTRACT signal on channel 40 which determine the direction of each increment of U- register 28 contents. The add-subtract devisions are based chiey upon the instantaneous state of r11-(p), the signal on channel 38. At the occurrence of clock pulse C3, the signal on channel 45 generated by the logic time base 31, the state of the n,(p) signal on channel 38 is sampled, and the resultant add or subtract decision is stored in a short-term devision memory. The ADD signal on channel 39 is in the true" state if the n,(p) signal on channel 38 was a logical one, and the SUBTRACT signal on channel 40 is in the true state if the nr(p) signal on channel 38 was a logical zero. Thus, it is seen that the direction of the U-register 28 increment is random, with a statistical bias dependent upon the instantaneous state of statistical source 26. That is, the probability of a positive or a negative increment of U-register 28 contents is a function of the probability control voltage, the signal on channel 37.

The U register 28 consists of counter lap-down steering logic 79 and a 4-stage reversible counter 80. The function implemented by U register 28 is that of a standard 4bit binary up-down counter, with fifteen of the sixteen possible counter states utilized. Limit gates within counter up-down steering logic 79 monitor the contents of 4 stage reversible counter 80 and detect the counts of one and fifteen. The counter up-down steering logic 79 senses the levels of the ADD signal on channel 39 and the SUBTRACT signal on channel 40 at the occurrence of clock pulse C4, the signal on channel 46 generated by the logic time base 31, and generates a COUNT-UP signal on channel 94 if the ADD signal on channel 39 is true and if a count of fifteen is not detected in the 4stage reversible counter 80. Conversely, a COUNT-DOWN signal on channel 95 is generated if the SUBTRACT signal on channel 40 is true and if a count of one is not detected in the 4-stage reversible counter 80. If the 4-stage reversible counter 80 is in either the one state or the fifteen state, it remains in that state until a true ADD signal on channel 39 or a true SUBTRACT signal on channel 40, respectively, is sensed at the time of occurrence of C4, the signal on channel 46. The COUNT-UP signal on channel 94 is described by the Boolean function while the COUNT-DOWN signal on channel 95 is described by The contents of U register 28, the signal on channel 41, are processed by D/A converter 29 to generate the u(t) plant control signal on channel 21 and its inverse, the -u(t) signal on channel 42. The u(t) signal on channel 21 is fed directly to the controlled plant 12, and both the u(t) signal on channel 21 and the u(t) signal on channel 42 are used by the sign Au(t) memory 30 to derive the direction of change of the 14(1) plant control signal on channel 2l, which is then stored for subsequent use in determining required changes in the control sysstem statistical bias. The D/A converter 29 consists of precision bit-weight resistors 81 and inverting operational amplifiers 82 and 83.

The actual D/A conversion is performed by precision bit-weight resistors 81, which comprise a standard resistive summation network. One end of a precision resistor is connected to the true output of each counter stage of the U register 28, and the other ends of the resistors are tied in common, forming a summation point. Since the value of each of the precision resistors differs from the value of adjacent resistors by a power of two, with the lowest value connected to the most significant bit and the highest value connected to the least signicant bit of U register 28, the summation point provides an analog voltage level, the signal on channel 96, that accurately represents the contents of U register 28. This analog voltage level is then amplified by inverting opera tional amplifier 82 to provide the bipolar plant control signal, u(t), the signal on channel 21. Another inverting operational amplifier 83 in series operates on the u(t) signal on channel 21 with a unity amplification factor to provide the inverse signal, u(t), the signal on channel 42.

The sign Au(t) memory 30, consisting of slope detectors 84 and 85, sgn nu temporary memory 86, and 4- stage shift register 87, monitors the u(t) signal on channel 21 and the -u(t) signal on channel 42 to determine the current direction of the increment, if any, of Uregis` ter 28 contents and then stores the direction of the increment, sgn Au, the signal on channel 48, in a register that always contains the direction of the four recent increments. The slope detector 84 monitors the u(t) signal on channel 21 and detects a positive transition in the signal to generate a pulse, the signal on channel 97, which indicates the current sgn nu was positive, In a like man ner, slope detector 85 monitors the -u(t) signal on channel 42 (the inverse of the 4(1) signal on channel 21) and detects a positive transition in the signal to generate a pulse, the signal on channel 98, which indicates the current sgn Au was negative. The pulse appearing on channel 97 or 98, indicating that sgn nu was positive or negative, respectively, sets or resets sgn Au temporary memory 86. Then, at the occurrence of clock pulse C5, the signal on channel 47 generated by the logic time base 31, the sgn Au information in sgn nu temporary memory 86 is transferred to a 4-stage shift register 87. At the beginning of any sample period t, the 4-stage shift register 87 contains, in stages 1-4, the sgn au information for sample periods t-l, t-Z, t-3, and t-4, respectively. The sgn Au delay select 32 determines from which register stage the sgn Au signal on channel 48 is obtained; i.e., to which prior sample period the sgn nu information pertains. ln this disclosure, a sgn Au signal on channel 48 equal to logical one indicates a positive increment in the MU) signal on channel 21, and a sgn nu signal on channel 48 equal to logical zero indicates a negative increment in the u(t) signal on channel 21.

The proper sequence of events within each sample period is maintained nby the logic time base 31, which generates clock pulses C1, the signal on channel 43; C2, the signal on channel 44; C3, the signal on channel 45; C4, the signal on channel 46; and C5, the signal on channel 47. A standard transistor oscillator 88 establishes the sample period repetition rate which may be varied by the sample rate control 33. The output signal on channel 99 of the oscillator 88 is delayed by varied amounts and shaped by the clock pulse delay and shaping network 89 to generate the sequential clock pulses. Although the logic time base described in this disclosure generates sample periods occurring at regular intervals of time, the self-organizing control system of this invention could as well incorporate an aperiodic or random logic time base, without regular time-spacing of sample periods and without set time intervals between the clock pulses in any given sample period. The only requirement is to provide C1, the signal on channel 43; C2, the signal on channel 44; C3, the signal on channel 45; C4, the signal on channel 46; and C5, the signal on channel 47, in the proper sequence as described in this disclosure.

The generalized electrical circuits and the circuit interconnections of the PSV conditioning logic 16 of FIG- URES 2 and 5 are detailed by the functional schematics of FIGURES 8 through 12. Specific component values and supply voltages are not shown since they are unique to the characteristics of a given controlled plant and to the characteristics of the components (such as the operational amplifiers, logic gates, and transistors) used for hardware implementation of the functional schematics. FIGURE 8 illustrates the functional schematic of P- register control logic 23, P register 24, and D/A converter 25. FIGURE 9 illustrates the functional schematic of statistical source 26. FIGURE 10 illustrates the functional schematic of U-register control logic 27, U register 28, and D/A converter 29. FIGURE 1l illustrates the functional schematic of sign Au(t) memory 30. FIG- URE 12 illustrates the functional schematic of logic time base 31.

As illustrated in the functional schematic of FIGURE 8, the P-register control logic 29, consisting of add-subtract decision logic 69 and decision memory 70, generates the ADD signal on channel 34 and the SUBTRACT signal on channel 35, based upon the correlation of the V signal on channel from the performance assessment stage 1S and the Sgn Au signal on channel 48 from the sign Anh) memory 30. The add or subtract decision is made by add-subtract decision logic 69. First, inverters 111 and 112 generate V and sgn Au, respectively. AND- gate 113 then forms the logical product Vsgn Au, and AND-gate 114 forms the logical product V-sgn Au. The balance of the inclusive-OR function is performed by OR-gate 117 which forms the logical sum of logical products, V'sgn Au U Vsgn du, defined as the add decision. At the same time, AND-gate 11S forms the logical product V@ and AND-gate 116 forms the logical product sgn nu. The balance of the exclusive- OR function is performed by OR-gate 118 which forms the logical sum of logical products, V'sgn du U V-sgn nu, defined as the subtract decision. A standard I-K ipop comprises decision memory 70, with the add decission output signal of OR-gate 117 applied to the setlogic input, and the subtract decision output signal of OR- gate 118 applied to the reset-logic input. At the occurrence of clock pulse C1, the signal on channel 43, at the trigger input, decision memory 70 assumes either the set or the reset state, dependent upon the existence of an add or a subtract decision. The ADD signal on channel 34, which occurs at the set output of decision memory 70, thus may be expressed as the Boolean function ADDzV-sgn nu U while the SUBTRACT signal on channel 35, which occurs at the reset output of decision memory 70, may be expressed as the Boolean function The functional schematic of FIGURE 8 depicts P register 24 as the counter up-down steering logic 71 and the i-stage reversible counter 72, which comprise a standard 3-bit binary up-down counter employing a ripplethrough count propagation based on intermediate dilierentiating networks. The counter up-down steering logic 71 consists of count pulse formation AND-gates 119 and 120, and counter limit AND-gates 121 and 122. The three bits, A, B, and C, of 3-stage reversible counter 72 (with bit A as the least significant bit) consist of standard J-K flip-flops 124, 128, and 132, respectively. Countter limit AND-gate 121 monitors the set outputs of bits A, B, and C, to detect the count of seven in P register 24, and to form the logical product A-B-C, or CNT 7, which acts as in inhibiting input to AND-gate 119. In a similar manner, counter limit AND-gate 122 monitors the set output of bit A and the reset outputs of bits B and C, to detect the count of one in P register 24, and to form the logical product A-F', or CNT 1, which acts as an inhibiting input to AND-gate 120. AND-gate 119 is strobed by C2, the signal on channel 44, to form a COUNT-UP pulse if the ADD signal on channel 34 is true and if the inhibiting input CNT 7 is not true. The COUNT-UP signal on channel formed by AND- gate 119 is thus described by the Boolean function ADDCNT7C2. Likewise, AND-gate 120 is strobed by C2, the signal on channel 44, to form a COUNT-DOWN pulse if the SUBTRACT signal on channel 3S is true and if the inhibiting input CNT 1 is not true. The COUNT-DOWN signal on channel 91, formed by AND- gate 120, is thus described by the Boolean function SUBNT -C2.

The three standard J-K ip-ops which form bits A, B, and C of 3-stage reversible counter 72 each have the set output tied to the reset-logic input and the reset output tied to the set-logic input, thus allowing a change of state to occur whenever a pulse occurs at the trigger input. The trigger input pulse for Hip-Hop 124 (bit A) is formed by OR-gate 123 which forms the logical sum of the COUNT-UP signal on channel 90 and the COUNT- DOWN signal on channel 91. Thus, bit A changes state at the occurrence of C2, the signal on channel 44, for either an add or a subtract decision, provided P register 24 is not in either of its two limit states, one and seven. The trigger input pulse for ip-op 128 (bit B) is provided by OR-gate 127 which forms the logical sum of the outputs of AND-gate and 126. Ditferentiating network RC,i forms a pulse when the reset output of ip-op 124 (bit A) changes from the logical zero state to the logical one state. AND-gate 125 then forms the logical product of this pulse and the COUNT-UP signal on channel 90. Similarly, differentiating network RbCb forms a pulse when the set output of Hip-flop 124 (bit A) changes from the logical zero state to the logical one state, and AND-gate 126 then forms the logical product of this pulse and the COUNT-DOWN signal on channel 91. Thus, flip-flop 128 (bit B) changes state whenever tiip-op 124 (bit A) assumes the reset state in response to a COUNT-UP pulse or assumes the set state in response to a COUNT-DOWN pulse. The trigger input pulse for ip-op 132 (bit C) is provided by OR-gate 131 which forms the logical sum of the outputs of AND-gates 129 and 130. Differentiating network RCc forms a pulse when the reset output of flip-flop 128 (bit B) changes from the logical zero state to the logical one state. AND-gate 129 then forms the logical product of this pulse and the COUNT-UP signal on channel 90. Likewise, dilferentiating network RdCd forms a pulse when the set output of flip-Hop 128 (bit B) changes from the logical zero state to the logical one state, and AND- gate 130 then forms the logical product of this pulse and the COUNT-DOWN Signal on channel 91. Thus, flip-flop 132 (bit C) changes state whenever ip-flop 128 (bit B) assumes the reset state as the result of a COUNT- UP pulse or assumes the set state as the result of a COUNT-DOWN pulse. It is seen from the above description that counter up-down steering logic 71 and 3- stage reversible counter 72 comprise a standard 3-bit binary up-down counter employing ripple-through count propagation.

FIGURE 8 also shows that the contents of P register 24 are processed by D/A converter 25, consisting of precision bit-weight resistors 73 and operational amplifier 74, to generate the statistical source probability control voltage, vp, the signal on channel 37. Precision resistor Rx, which is connected to the set output of flip-op 132 (bit C of P register 24); resistor 2Rx, which is connected to the set output of Hip-flop 128 (bit B of P register 24); and resistor 4RX, which is connected to the set output of flip-Hop 124 (bit A of P register 24), form a standard resistive summation network. Due to the ratio of the values of the precision resistors, the voltage level at the summation point (the signal on channel 92) represents an accurate digital-to-analog conversion of the contents of P register 24. This analog voltage level is then amplified by standard operational amplitier 74 to form the bipolar vp signal on channel 37. Resistor Re provides feedback to insure a stable amplification factor. Capacitor C compensates for the amplifier input capacitance to prevent phase shift. As illustrated, provision is made to adjust the over-all gain of the amplification stage, and to compensate for the inherent DC offset of amplifier 74.

The generalized schematic of statistical source 26 is detailed in the functional schematic of FIGURE 9. The statistical source 26 consists of random noise generator 76, threshold comparator 75, and output buffer 77, and generates a random sequence of logical ones and logical zeroes, the nr( p) signal on channel 38, with a probabilistic duty cycle controlled by the output of P register 24, the signal on channel 37. The random noise generator 76 consists of a critically-biased Zener diode 133 which acts as a noise source with approximately Gaussian distribution, and cascaded standard linear amplifier stages 134, 135, and 136, which provide the required gain of several thousand. The output of the random noise generator 76, nr, the signal on channel 93, and the vp signal on channel 37, plus a correlated secondary comparator voltage formed by inverting emitter follower 141, are then processed by threshold comparator 75, consisting of series emitter-coupled clipper stages 137, 138 and 139, 140 to generate a signal that is a random sequence of voltage excursions between high and low levels with a duty cycle in direct proportion to the magnitude and polarity of the vp signal on channel 37. The resultant signal is then operated on by level changer 142 and Shaper 143 to provide the statistical source output, n,(p), the signal on channel 38, which is a random series of logical ones and logical zeroes with a probabilistically-controlled duty cycle.

FIGURE detals the generalized schematic of U- register control logic 27, U register 28, and D/A converter 29. The add-subtract decision logic and memory 78 generates the ADD signal on channel 39 and the SUB- TRACT signal on channel 40 which determine the direction of the increment to the contents of U register 28, based upon the instantaneous state of the biased random signal n,(p), on channel 38. The statistical source output signal on channel 38 is applied to the set-logic input, and its complement (formed by inverter 144) is applied to the reset-logic input, of a standard I-K Hip-Hop 145. At the occurrence of clock pulse C3, the signal on channel 45, at the trigger input, ip-op 145 assumes either the set or reset state, dependent upon the instantaneous state of the statistical source output signal. The ADD signal on channel 39, which occurs at the set output of ip-fiop 145, is a logical one if the instantaneous state of the n,(p) signal on channel 38 was a logical one. Conversely, the SUBTRACT signal on channel 40, which occurs at the reset output of fiip-op 145, is a logical one of the instantaneous state if the n,(p) signal on channel 38 was a logical zero.

The functional schematic of FIGURE 10 depicts U register 28 as the counter up-down steering logic 79 and the 4-stage reversible counter 80, which comprise a standard 4-bit binary up-down counter employing a ripple-through count propagation based on intermediate differentiating networks. The counter up-down steering logic 79 consists of count pulse formation AND-gates 146 and 147, and counter limit AND-gates 148 and 149. The four bits, A, B, C, and D of 4-stage reversible counter 80 (with bit A as the least significant bit) consist of standard I-K flip-flops 151, 155, 159, and 163, respectively. Counter limit AND-gate 148 monitors the set outputs of bits A, B, C, and D, to detect the count of fifteen in U register 28, and to form the logical product A-B-C-D, or the CNT signal on channel 164, which acts as an inhibiting input to AND-gate 146. In a similar manner, counter limit AND-gate 149 monitors the set output of bit A and the reset outputs of bits B, C, and

D, to detect the count of one in U register 28, and to form the logical product A B'1, or the CNT 1 signal on channel 165, which acts as an inhibiting input to AND-gate 147. AND-gate 146 is strobed by C4, the signal on channel 46, to form a COUNT-UP pulse if the ADD signal on channel 39 is true and if the inhibiting input, the CNT 15 signal on channel 164, is not true. The COUNT-UP signal on channel 94 formed by AND- gate 146 is thus described by the Boolean function ADD'CNT 'f5-C4. Likewise, AND-gate 147 is strobed by C4, the signal on channel 46, to form a COUNT- `DOWN PULSE if the SUBTRACT signal on channel 40 is true and if the inhibiting input, the CNT 1 signal on channel 165, is not true. The COUNT-DOWN signal on channel formed by AND-gate 147 is thus described by the Boolean function SUB 'C4.

The four standard I-K flip-flops which form bits A, B, C, and D of 4stage reversible counter `80 each have the set output tied to the reset-logic input and the reset output tied to the set-logic input, thus allowing a change of state to occur whenever a pulse occurs at the trigger input. The trigger input pulse for Hip-flop 151 (bit A) is formed by OR-gate 150 which forms the logical sum of the COUNT- UP signal on channel 94 and the COUNT-DOWN signal on channel 95. Thus, bit A changes state at the occurrence of C4, the signal on channel 46, for either an add or subtract decision, provided U register 28 is not in either of its two limit states, one and fifteen. The trigger input pulse for fiip-fiop (bit B) is provided by OR-gate 154 which forms the logical sum of the outputs of AND-gates 152 and 153. Differentiating network RfCf forms a pulse when the reset output of flip-dop 151 (bit A) changes from the logcal zero state to the logical one state. AND- gate 152 then forms the logical product of this pulse and the COUNT-UP signal on channel 94. Similarly, difierentiating network RECrg forms a pulse when the set output of Hip-flop 151 (bit A) changes from the logical zero state to the logical one state, and AND-gate 153 then forms the logical product of this pulse and the COUNT- DOWN signal on channel 95. Thus, fiip-flop 155 (bit B) changes state whenever ilip-op 151 (bit A) assumes the reset state in response to a COUNT-UP pulse or assumes the set state in response to a COUNT-DOWN pulse. The trigger input pulse for flip-hop 159 (bit C) is provided by OR-gate 158 which forms the logical sum of the outputs of AND-gates 156 and 157. Ditferentiating network RhCh forms a pulse when the reset output of flip-tiop 155 (bit B) changes from the logical zero state to the logical one state. AND-gate 156 then forms the logical product of this pulse and the COUNT-UP signal on channel 94. Likewise, differentiating network R,C, forms a pulse when the yset output of flip-Hop 155 (bit B) changes from the logical zero state to the logical one state, and AND-gate 157 then forms the logical product of this pulse and the COUNT-DOWN signal on channel 95. Thus, ip-iiop 159 (bit C) changes state whenever fiip-fiop 155 (bit B) assumes the reset state as the result of a COUNT-UP pulse or assumes the set state as the result of a COUNT- DOWN pulse. The trigger input pulse for flip-hop 163 (bit D) is provided lby yOR-gatie 162 which forms the logical sum of the outputs of AND-gates 160 and 161. Differentiating network RIC, forms a pulse when the reset output of Hip-flop 159 (bit C) changes from the logical zero state to the logical one state. AND-gate 160 then forms the logical prod-uct of this pulse and the COUNT- UP signal on channel 94. Likewise, differentiating network RkCk forms a pulse when the set output of ip-op 159 (bit C) changes from the logical zero state to the logical one state, and AND-gate 161 then forms the logical product of this pulse and the COUNT-DOWN signal on channel 95. Thus, Hip-flop 163 (bit D) changes state whenever ip-op 159 (bit C) assumes the reset state as the result of a COUNT-UP pulse or assumes the set state as the result of a COUNT-DOWN pulse. It is seen from 

